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Pole–zero plot
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<h2 id="continuous-time-systems">Continuous-time systems</h2> <p>In general, a <a href="/facts/Rational_function/2nJGu0Ko">rational</a> transfer function for a continuous-time <a href="/facts/LTI_system_theory/kEmj0QDC">LTI system</a> has the form: </p><p> H ( s ) = B ( s ) A ( s ) = ∑ m = 0 M b m s m s N + ∑ n = 0 N − 1 a n s n = b 0 + b 1 s + b 2 s 2 + ⋯ + b M s M a 0 + a 1 s + a 2 s 2 + ⋯ + a ( N − 1 ) s ( N − 1 ) + s N {\displaystyle H(s)={\frac {B(s)}{A(s)}}={\displaystyle \sum _{m=0}^{M}{b_{m}s^{m}} \over s^{N}+\displaystyle \sum _{n=0}^{N-1}{a_{n}s^{n}}}={\frac {b_{0}+b_{1}s+b_{2}s^{2}+\cdots +b_{M}s^{M}}{a_{0}+a_{1}s+a_{2}s^{2}+\cdots +a_{(N-1)}s^{(N-1)}+s^{N}}}} </p><p>where </p> <ul><li> B {\displaystyle B} and A {\displaystyle A} are polynomials in s {\displaystyle s} ,</li> <li> M {\displaystyle M} is the order of the numerator polynomial,</li> <li> b m {\displaystyle b_{m}} is the m {\displaystyle m} th coefficient of the numerator polynomial,</li> <li> N {\displaystyle N} is the order of the denominator polynomial, and</li> <li> a n {\displaystyle a_{n}} is the n {\displaystyle n} th coefficient of the denominator polynomial.</li></ul> <p>Either M {\displaystyle M} or N {\displaystyle N} or both may be zero, but in real systems, it should be the case that M ≤ N {\displaystyle M\leq N} ; otherwise the gain would be unbounded at high frequencies. </p> <h3>Poles and zeros</h3> <ul><li>the zeros of the system are roots of the numerator polynomial: s = { β m ∣ m ∈ 1 , … M } {\displaystyle s=\{\beta _{m}\mid m\in 1,\ldots M\}} such that B ( s ) | s = β m = 0 {\displaystyle B(s)|_{s=\beta _{m}}=0} </li> <li>the poles of the system are roots of the denominator polynomial: s = { α n ∣ n ∈ 1 , … N } {\displaystyle s=\{\alpha _{n}\mid n\in 1,\ldots N\}} such that A ( s ) | s = α n = 0. {\displaystyle A(s)|_{s=\alpha _{n}}=0.} </li></ul> <h3>Region of convergence</h3> <p class="note">See also: <a href="/facts/Laplace_transform/0Ge4MIc9">Laplace transform § Region of convergence</a></p> <p>The <a href="/facts/Region_of_convergence/4Un0ANfP">region of convergence</a> (ROC) for a given continuous-time transfer function is a half-plane or vertical strip, either of which contains no poles. In general, the ROC is not unique, and the particular ROC in any given case depends on whether the system is <a href="/facts/Causal_system/68Dch3YW">causal</a> or anti-causal. </p> <ul><li>If the ROC includes the <a href="/facts/Imaginary_axis/6Xh9W3hq">imaginary axis</a>, then the system is <a href="/facts/BIBO_stability/RxD8h2f5">bounded-input, bounded-output (BIBO) stable</a>.</li> <li>If the ROC extends rightward from the pole with the largest <a href="/facts/Complex_number/2w7mqI7e">real-part</a> (but not at infinity), then the system is causal.</li> <li>If the ROC extends leftward from the pole with the smallest real-part (but not at negative infinity), then the system is anti-causal.</li></ul> <p>The ROC is usually chosen to include the imaginary axis since it is important for most practical systems to have <a href="/facts/BIBO_stability/RxD8h2f5">BIBO stability</a>. </p> <h3>Example</h3> <p> H ( s ) = 25 s 2 + 6 s + 25 {\displaystyle H(s)={\frac {25}{s^{2}+6s+25}}} </p><p>This system has no (finite) zeros and two poles: s = α 1 = − 3 + 4 j {\displaystyle s=\alpha _{1}=-3+4j} and s = α 2 = − 3 − 4 j {\displaystyle s=\alpha _{2}=-3-4j} </p><p>The pole-zero plot would be: </p><p>Notice that these two poles are <a href="/facts/Complex_conjugate/7TEaoQDe">complex conjugates</a>, which is the necessary and sufficient condition to have real-valued coefficients in the differential equation representing the system. </p> <h2 id="discrete-time-systems">Discrete-time systems</h2> <p>In general, a rational transfer function for a discrete-time <a href="/facts/LTI_system_theory/kEmj0QDC">LTI system</a> has the form: </p><p> H ( z ) = P ( z ) Q ( z ) = ∑ m = 0 M b m z − m 1 + ∑ n = 1 N a n z − n = b 0 + b 1 z − 1 + b 2 z − 2 ⋯ + b M z − M 1 + a 1 z − 1 + a 2 z − 2 ⋯ + a N z − N {\displaystyle H(z)={\frac {P(z)}{Q(z)}}={\frac {\displaystyle \sum _{m=0}^{M}{b_{m}z^{-m}}}{1+\displaystyle \sum _{n=1}^{N}{a_{n}z^{-n}}}}={\frac {b_{0}+b_{1}z^{-1}+b_{2}z^{-2}\cdots +b_{M}z^{-M}}{1+a_{1}z^{-1}+a_{2}z^{-2}\cdots +a_{N}z^{-N}}}} </p><p>where </p> <ul><li> M {\displaystyle M} is the order of the numerator polynomial,</li> <li> b m {\displaystyle b_{m}} is the m {\displaystyle m} th coefficient of the numerator polynomial,</li> <li> N {\displaystyle N} is the order of the denominator polynomial, and</li> <li> a n {\displaystyle a_{n}} is the n {\displaystyle n} th coefficient of the denominator polynomial.</li></ul> <p>Either M {\displaystyle M} or N {\displaystyle N} or both may be zero. </p> <h3>Poles and zeros</h3> <ul><li> z = β m {\displaystyle z=\beta _{m}} such that P ( z ) | z = β m = 0 {\displaystyle P(z)|_{z=\beta _{m}}=0} are the <a href="/facts/Zero_(complex_analysis)/gnA3U8VP">zeros</a> of the system</li> <li> z = α n {\displaystyle z=\alpha _{n}} such that Q ( z ) | z = α n = 0 {\displaystyle Q(z)|_{z=\alpha _{n}}=0} are the <a href="/facts/Pole_(complex_analysis)/gnA3U8VP">poles</a> of the system.</li></ul> <h3>Region of convergence</h3> <p class="note">See also: <a href="/facts/Z-transform/ERNvDJqt">Z-transform § Region of convergence</a></p> <p>The <a href="/facts/Region_of_convergence/4Un0ANfP">region of convergence</a> (ROC) for a given discrete-time transfer function is a <a href="/facts/Disk_(mathematics)/DgMVr97H">disk</a> or <a href="/facts/Annulus_(mathematics)/rhxKuoem">annulus</a> which contains no uncancelled poles. In general, the ROC is not unique, and the particular ROC in any given case depends on whether the system is <a href="/facts/Causal_system/68Dch3YW">causal</a> or anti-causal. </p> <ul><li>If the ROC includes the <a href="/facts/Unit_circle/VsTffjPK">unit circle</a>, then the system is <a href="/facts/BIBO_stability/RxD8h2f5">bounded-input, bounded-output (BIBO) stable</a>.</li> <li>If the ROC extends outward from the pole with the largest (but not infinite) magnitude, then the system has a right-sided impulse response. If the ROC extends outward from the pole with the largest magnitude and there is no pole at infinity, then the system is causal.</li> <li>If the ROC extends inward from the pole with the smallest (nonzero) magnitude, then the system is anti-causal.</li></ul> <p>The ROC is usually chosen to include the unit circle since it is important for most practical systems to have <a href="/facts/BIBO_stability/RxD8h2f5">BIBO stability</a>. </p> <h3>Example</h3> <p>If P ( z ) {\displaystyle P(z)} and Q ( z ) {\displaystyle Q(z)} are completely factored, their solution can be easily plotted in the <a href="/facts/Z-transform/ERNvDJqt">z-plane</a>. For example, given the following transfer function: H ( z ) = z + 2 z 2 + 1 4 {\displaystyle H(z)={\frac {z+2}{z^{2}+{\frac {1}{4}}}}} </p><p>The only (finite) zero is located at: z = − 2 {\displaystyle z=-2} , and the two poles are located at: z = ± j 2 {\displaystyle z=\pm {\frac {j}{2}}} , where j {\displaystyle j} is the <a href="/facts/Imaginary_unit/1SCllQlU">imaginary unit</a>. </p><p>The pole–zero plot would be: </p> <h2 id="see-also">See also</h2> <ul><li><a href="/facts/Root_locus/PHASdGw7">Root locus</a></li> <li><a href="/facts/Laplace_transform/0Ge4MIc9">Laplace transform</a></li> <li><a href="/facts/Z-transform/ERNvDJqt">Z-transform</a></li> <li><a href="/facts/Rational_function/2nJGu0Ko">Rational function</a></li></ul> <h2 id="bibliography">Bibliography</h2> <ul><li>Haag, Michael (June 22, 2005). <a href="https://cnx.org/contents/3ktflSan@13/Understanding-PoleZero-Plots-o">"Understanding Pole/Zero Plots on the Z-Plane"</a>. <i><a href="/facts/OpenStax_CNX/hI4yPb5L">OpenStax CNX</a></i>. Retrieved June 9, 2018.[<i>dead link</i>]</li> <li><a href="/facts/Eric_W._Weisstein/FbMuVDep">Eric W. Weisstein</a>. <a href="http://mathworld.wolfram.com/Z-Transform.html">"Z-Transform"</a>. <i><a href="/facts/MathWorld/yc1jodbq">MathWorld</a></i>. Retrieved January 24, 2010.</li></ul>